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S parameters characterize any RF device s behavior at different frequencies and bias points With the information that S parameters supply, the designer can calculate a device s gain, return loss, stability, reverse isolation, and its input and output impedances Knowing the transistor s port impedances is required so that the necessary matching network can easily be designed for a proper impedance match from stage to stage This matching is vital so that maximum power is delivered to the load at a high return loss (minimum power reflected back toward the source from the load) Impedance matching of active devices is essential because not only will the typical transistor not have a 50-ohm resistive ZIN and ZOUT, but its reactances will also vary over frequency This means that for maximum power transfer into the system s impedance, which is normally 50 ohms, a matching network must be used to match the active device to the system s impedance, and sometimes over a wide band of frequencies However, utilizing LC components is the dominant matching technique, so the match will be perfect only over a very narrow band of frequencies There are, nevertheless, techniques for impedance matching that work quite well over a very wide band of frequencies, and these will be discussed For further information, consult the influential work on practical amplifier design RF Circuit Design by Chris Bowick As mentioned above, a device that must be matched will normally not be at 50 ohms resistive and furthermore will be either inductive or capacitive This combination resistive and reactive elements in the active device s ZIN and ZOUT is referred to as a complex impedance So the matching network s job is not only to match the active device to the system s impedance, but also to cancel the reactive element to allow for a 50 j0 match (or 50 ohms resistive, with no capacitive or inductive reactances) This is called conjugate matching, and supplies a perfect impedance match Nevertheless, in order to decrease the gain of a transistor at various desired frequencies for gain flattening, or to purposely design an amplifier with less gain within its bandpass, as well as for optimal noise figure (NF), a perfect match may not be desired for certain amplifier applications It is usually advisable that all circuits, even discrete circuits in the middle of an IF chain, have a ZIN and ZOUT of 50 ohms Although we could match at any sensible impedance from discrete stage to discrete stage, it would make it quite difficult to perform accurate interstage tests with the 50-ohm test gear commonly available Thus, after each stage is tested, a 50-ohm circuit can then be confidently placed within the system for reliable cascaded operation When designing matching networks, we will take the S-parameter 2-port representation of the transistor, ignoring any effect the DC biasing network may have on these parameters in the final design This is quite valid if only small amounts of RF feedback are produced by high values of Rf (Fig 315; the feedback resistor) in an amplifier s bias network In this way, the S parameters will be satisfactory for computing not only the matching networks, but also for the software simulations of the circuit s responses However, if an amplifier utilizes a low value resistor for Rf in order to employ heavy feedback,.

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then the S parameters may no longer be completely valid In other words, the amplifier circuit s attributes, as defined by the device s S parameters, are accurate only when the bias network employs the normal, high value of bias resistors within its bias network S-parameter files (or *S2P; Fig 316) contain only the parameters for a few frequencies (usually not more than 20), so when reading S parameters on data sheets, or in the *S2P text files themselves, we may find that our frequency of interest falls between two values For accuracy, we will take the mean value between the two closest frequencies As an example: S parameters are given in a certain *S2P file for 3 GHz and 4 GHz, but our design requires a center frequency of 35 GHz Take the mean value of each S parameter at 3 GHz and 4 GHz To compute S12 at 35 GHz: S12MAG (@ 3 GHz) 2 and S12 (@ 3 GHz) 2 S12 (@ 4 GHz) S12 (@ 35 GHz) S12MAG (@ 4 GHz) S12MAG (@ 35 GHz)

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The simple analysis of S parameters will furnish the designer with a lot of data on the active device of interest, such as three different ranges of possible gains: the maximum available gain (MAG) that the transistor can attain when perfectly

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